參數(shù)資料
型號(hào): KH561AI
廠商: FAIRCHILD SEMICONDUCTOR CORP
元件分類: 運(yùn)動(dòng)控制電子
英文描述: Wideband, Low Distortion Driver Amplifier
中文描述: OP-AMP, 5000 uV OFFSET-MAX, CDIP24
封裝: CERAMIC, DIP-24
文件頁(yè)數(shù): 10/13頁(yè)
文件大小: 182K
代理商: KH561AI
DATA SHEET
KH561
10
REV. 1A February 2001
output with the same gain as the input signal, while the
inverting current errors have a gain of simply (R
f
- R
o
) to
the output voltage (neglecting the R
o
to R
L
attenuation).
Output DC Offset:
The DC error terms shown in the specification listing
along with the model of Figure 5 may be used to estimate
the output DC offset voltage and drift. Each term shown
in the specification listing can be of either polarity. While
the equations shown below are for output offset voltage,
the same equation may be used for the drift with each
term replaced by its temperature drift value shown in the
specification listing.
Recall that the source impedance, R
s
, includes both the
terminating and signal source impedance and that the
actual DC level to the load includes the voltage divider
between R
o
and R
L
. Also note that for the KH561, as well
as for all current feedback amplifiers, the non-inverting
and inverting bias currents do not track each other in
either magnitude or polarity. Hence, there is no meaning
in an offset current specification, and source impedance
matching to cancel bias currents is ineffective.
Noise Analysis:
Although the DC error terms are in fact random, the cal-
culation shown above assumes they are all additive in a
worst case sense. The effect of all the various noise
sources are combined as a root sum of squared terms to
get an overall expression for the spot noise voltage. The
circuit of Figure 8 shows the equivalent circuit with all the
various noise voltages and currents included along with
their gains to the output.
where:
Gain to e
o
e
ni
non-inverting input voltage noise
i
ni
non-inverting input current noise
i
i
inverting input current noise
4
kTR
sourceresis
noise
A
v
A
v
R
s
R
f
- R
o
A
v
R
f
- R
o
1
1
Figure 8: Equivalent Noise Model
To get an expression for the equivalent output noise volt-
age, each of these noise voltage and current terms must
be taken to the output through their appropriate gains
and combined as the root sum of squares.
Where the 4kT(R
f
- R
o
) A
v
term is the combined noise
power of R
g
and R
f
- R
o
.
It is often more useful to show the noise as an equivalent
input spot noise voltage where every term shown above
is reflected to the input. This allows a direct measure of
the input signal to noise ratio. This is done by dividing
every term inside the radical by the signal voltage gain
squared. This, and an example calculation for the circuit
of Figure 1, are shown below.
neglected in this calculation.
Note that R
L
may be
V
I
R
V
1
R
R
R
I
R
(
R
where: I
non invertingbias current
invertingbias current
input offset voltage
I
V
V
5 A 25
2.0mV 10 10 A 360
12.4mV
= ±
attentuationbetweenR andR
os
bn
s
io
f
o
g
bi
f
o
bn
bi
io
o
L
1/ 2
=
±
(
)
+
±
)
=
±
(
)
[
]
L
An example calculation for the circuit in Figure 1 using
typical 25
°
C DC error terms and R
s
= 25
, R
L
= 50
yields:
R
g
i
i
e
o
R
o
R
f
- R
o
Classical
op-amp
-
+
4kTRV
o
4kT(R
f
- R
o
)
*
*
4kTR
s
4kT
R
g
*
*
R
s
i
ni
*
*
e
ni
*
4
4
4
ce voltage
kT R
gainsettlingresistor
noise current
kT R
R
feedback resistor
voltagenoise
kTR
outputresistor voltagenoise
s
g
f
o
o
)
tan
/
e
e
i R
kTR
4
A
i
R
(
)
R
kT R
4
R
A
kTR
4
o
ni
s
v
i
f
o
f
o
v
o
=
+
(
)
+
(
)
+
)
+
+
2
2
2
2
2
L
e
e
i R
kTR
4
i
R
(
R
2
A
kT R
4
R
A
kTR
A
v
n
ni
s
i
f
o
v
)
+
f
o
v
o
=
+
(
)
+
+
)
+
2
2
2
2
2
4
L
DC
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