參數(shù)資料
型號(hào)： AD629BR-REEL7
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 5/16頁(yè)
文件大小： 0K
描述： IC AMP DIFF 25MA LDRIFT 8SOIC
設(shè)計(jì)資源： Measuring -48 V High-Side Current Using AD629, AD8603, AD780, and AD7453 (CN0100)
標(biāo)準(zhǔn)包裝： 1,000
放大器類型： 差分
電路數(shù)： 1
轉(zhuǎn)換速率： 2.1 V/µs
-3db帶寬： 500kHz
電壓 - 輸入偏移： 100µV
電流 - 電源： 900µA
電流 - 輸出 / 通道： 25mA
電壓 - 電源，單路/雙路(±)： 5 V ~ 36 V，±2.5 V ~ 18 V
工作溫度： -40°C ~ 85°C
安裝類型： 表面貼裝
封裝/外殼： 8-SOIC（0.154"，3.90mm 寬）
供應(yīng)商設(shè)備封裝： 8-SO
包裝： 帶卷 (TR)
AD629
Rev. C | Page 13 of 16
OUTPUT CURRENT AND BUFFERING
The AD629 is designed to drive loads of 2 kΩ to within 2 V of
the rails but can deliver higher output currents at lower output
voltages (see Figure 17). If higher output current is required, the
output of the AD629 should be buffered with a precision op amp,
such as the OP113, as shown in Figure 38. This op amp can swing
to within 1 V of either rail while driving a load as small as 600 Ω.
REF (–)
REF (+)
–VS
+VS
VOUT
NC
–IN
+IN
0.1F
NC = NO CONNECT
21.1k
380k
20k
380k
AD629
1
2
3
4
8
7
6
5
007
83-
0
36
OP113
Figure 38. Output Buffering Application
A GAIN OF 19 DIFFERENTIAL AMPLIFIER
While low level signals can be connected directly to the –IN and
+IN inputs of the AD629, differential input signals can also be
connected, as shown in Figure 39, to give a precise gain of 19.
However, large common-mode voltages are no longer permissible.
Cold junction compensation can be implemented using a
temperature sensor, such as the AD590.
REF (–)
REF (+)
+VS
NC
–IN
+IN
0.1F
NC = NO CONNECT
21.1k
380k
20k
380k
AD629
1
2
3
4
8
7
6
5
00
783
-037
VOUT
VREF
THERMOCOUPLE
Figure 39. A Gain of 19 Thermocouple Amplifier
ERROR BUDGET ANALYSIS EXAMPLE 1
In the dc application that follows, the 10 A output current from
a device with a high common-mode voltage (such as a power
supply or current-mode amplifier) is sensed across a 1 Ω shunt
resistor (see Figure 40). The common-mode voltage is 200 V,
and the resistor terminals are connected through a long pair of
lead wires located in a high noise environment, for example,
50 Hz/60 Hz, 440 V ac power lines. The calculations in Table 7
assume an induced noise level of 1 V at 60 Hz on the leads, in
addition to a full-scale dc differential voltage of 10 V. The error
budget table quantifies the contribution of each error source.
Note that the dominant error source in this example is due to
the dc common-mode voltage.
REF (–)
OUTPUT
CURRENT
60Hz
POWER LINE
1
SHUNT
REF (+)
–VS
+VS
VOUT
NC
–IN
+IN
0.1F
NC = NO CONNECT
21.1k
380k
20k
380k
AD629
1
2
3
4
8
7
6
5
0
78
3
-03
8
10 AMPS
200VCMDC
TO GROUND
Figure 40. Error Budget Analysis Example 1: VIN = 10 V Full-Scale,
VCM = 200 V DC, RSHUNT = 1 Ω, 1 V p-p, 60 Hz Power-Line Interference
Table 7. AD629 vs. INA117 Error Budget Analysis Example 1 (VCM = 200 V dc)
Error, ppm of FS
Error Source
AD629
INA117
AD629
INA117
ACCURACY, TA = 25°C
Initial Gain Error
(0.0005 × 10)/10 V × 106
500
Offset Voltage
(0.001 V/10 V) × 106
(0.002 V/10 V) × 106
100
200
DC CMR (Over Temperature)
(224 × 10-6 × 200 V)/10 V × 106
(500 × 10-6 × 200 V)/10 V × 106
4480
10,000
Total Accuracy Error
5080
10,700
TEMPERATURE DRIFT (85°C)
Gain
10 ppm/°C × 60°C
600
Offset Voltage
(20 μV/°C × 60°C) × 106/10 V
(40 μV/°C × 60°C) × 106/10 V
120
240
Total Drift Error
720
840
RESOLUTION
Noise, Typical, 0.01 Hz to 10 Hz, μV p-p
15 μV/10 V × 106
25 μV/10 V × 106
2
3
CMR, 60 Hz
(141 × 10-6 × 1 V)/10 V × 106
(500 × 10-6 × 1 V)/10 V × 106
14
50
Nonlinearity
(10-5 × 10 V)/10 V × 106
10
Total Resolution Error
26
63
Total Error
5826
11,603
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