參數(shù)資料
型號(hào)： AD8599ARZ-REEL7
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 7/20頁(yè)
文件大小： 0K
描述： IC OPAMP GP 10MHZ DUAL ULN 8SOIC
設(shè)計(jì)資源： Using AD8599 as an Ultralow Distortion Driver for the AD7991 (CN0043)
Using AD8599 as an Ultralow Distortion Driver for the AD7995 (CN0044)
Using AD8599 as an Ultralow Distortion Driver for the AD7999 (CN0045)
High Speed Instrumentation Amplifier Using AD8271 and ADA4627-1 (CN0122)
標(biāo)準(zhǔn)包裝： 1,000
放大器類(lèi)型： 通用
電路數(shù)： 2
轉(zhuǎn)換速率： 16 V/µs
增益帶寬積： 10MHz
電流 - 輸入偏壓： 25nA
電壓 - 輸入偏移： 10µV
電流 - 電源： 5mA
電流 - 輸出 / 通道： 52mA
電壓 - 電源，單路/雙路(±)： 9 V ~ 36 V，±4.5 V ~ 18 V
工作溫度： -40°C ~ 125°C
安裝類(lèi)型： 表面貼裝
封裝/外殼： 8-SOIC（0.154"，3.90mm 寬）
供應(yīng)商設(shè)備封裝： 8-SO
包裝： 帶卷 (TR)
Data Sheet
AD8597/AD8599
Rev. E | Page 15 of 20
FUNCTIONAL OPERATION
INPUT VOLTAGE RANGE
The AD8597/AD8599 are not rail-to-rail input amplifiers;
therefore, care is required to ensure that both inputs do not
exceed the input voltage range. Under normal negative feedback
operating conditions, the amplifier corrects its output to ensure
that the two inputs are at the same voltage. However, if either
input exceeds the input voltage range, the loop opens and large
currents begin to flow through the ESD protection diodes in the
amplifier.
These diodes are connected between the inputs and each supply
rail to protect the input transistors against an electrostatic discharge
event and they are normally reverse-biased. However, if the
input voltage exceeds the supply voltage, these ESD diodes can
become forward-biased. Without current limiting, excessive
amounts of current may flow through these diodes, causing
permanent damage to the device. If inputs are subject to over-
voltage, insert appropriate series resistors to limit the diode
current to less than 5 mA maximum.
The input stage has two diodes between the input pins to protect
the differential pair. Under high slew rate conditions, when the
op amp is connected as a voltage follower, the diodes may become
forward-biased and the source may try to drive the output.
Place a small resistor in the feedback loop and in the noninverting
input. The noise of a 100 Ω resistor at room temperature is
~1.25 nV/√Hz, which is higher than the AD8597/AD8599.
Thus, there is a tradeoff between noise performance and
protection. If possible, place limiting earlier in the signal path.
For further details, see the Amplifier Input Protection… Friend
Because of the large transistors used to achieve low noise, the
input capacitance may seem rather high. To take advantage of
the low noise performance, impedance around the op amp must
be low, less than 500 Ω. Under these conditions, the pole from
the input capacitance must be greater than 50 MHz, which does
not affect the signal bandwidth.
OUTPUT PHASE REVERSAL
Output phase reversal occurs in some amplifiers when the input
common-mode voltage range is exceeded. As the common-mode
voltage is moved outside the input voltage range, the outputs of
these amplifiers can suddenly jump in the opposite direction to
the supply rail. This is the result of the differential input pair
shutting down that causes a radical shifting of internal voltages
that results in the erratic output behavior.
The AD8597/AD8599 amplifiers are carefully designed to prevent
any output phase reversal if both inputs are maintained within
the specified input voltage range. If one or both inputs exceed
the input voltage range but remain within the supply rails, the
op amp specifications, such as CMRR, are not guaranteed, but
the output remains close to the correct value.
NOISE AND SOURCE IMPEDANCE CONSIDERATIONS
The AD8597/AD8599 ultralow voltage noise of 1.1 nV/√Hz is
achieved with special input transistors running at high collector
current. Therefore, it is important to consider the total input-
referred noise (eN total), which includes contributions from
voltage noise (eN), current noise (iN), and resistor noise
(√4 kTRS).
eN total = [eN2 + 4 kTRS + (iN × RS)2]1/2
(1)
where RS is the total input source resistance.
This equation is plotted for the AD8597/AD8599 in Figure 58.
Because optimum dc performance is obtained with matched
source resistances, this case is considered even though it is clear
from Equation 1 that eliminating the balancing source resistance
lowers the total noise by reducing the total RS by a factor of 2.
At a very low source resistance (RS < 50 Ω), the voltage noise of the
amplifier dominates. As source resistance increases, the Johnson
noise of RS dominates until a higher resistance of RS > 2 kΩ is
achieved; the current noise component is larger than the
resistor noise.
100
1
10
0.1
10
100
1k
10k
TOTA
L
N
OIS
E
(
nV
/
H
z
)
SOURCE RESISTANCE (Ω)
06274-
076
TOTAL NOISE
RESISTOR NOISE
ONLY
Figure 58. Noise vs. Source Resistance
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