參數(shù)資料
型號(hào)： AD9632-EB
廠(chǎng)商： ANALOG DEVICES INC
元件分類(lèi)： 運(yùn)動(dòng)控制電子
英文描述： Ultralow Distortion, Wide Bandwidth Voltage Feedback Op Amps
中文描述： OP-AMP, UUC5
文件頁(yè)數(shù)： 13/20頁(yè)
文件大?。?/td> 528K
代理商： AD9632-EB
AD9631/AD9632
REV. A
–13–
THEORY OF OPERATION
General
The AD9631 and AD9632 are wide bandwidth, voltage feed-
back amplifiers. Since their open-loop frequency response fol-
lows the conventional 6 dB/octave roll-off, their gain bandwidth
product is basically constant. Increasing their closed-loop gain
results in a corresponding decrease in small signal bandwidth.
This can be observed by noting the bandwidth specification
between the AD9631 (gain of 1) and AD9632 (gain of 2). The
AD9631/AD9632 typically maintain 65 degrees of phase mar-
gin. This high margin minimizes the effects of signal and noise
peaking.
Feedback Resistor Choice
The value of the feedback resistor is critical for optimum perfor-
mance on the AD9631 (gain +1) and less critical as the gain in-
creases. Therefore, this section is specifically targeted at the
AD9631.
At minimum stable gain (+1), the AD9631 provides optimum
dynamic performance with R
F
= 140
. This resistor acts only
as a parasitic suppressor against damped RF oscillations that
can occur due to lead (input, feedback) inductance and parasitic
capacitance. This value of R
F
provides the best combination of
wide bandwidth, low parasitic peaking, and fast settling time.
In fact, for the same reasons, a 100–130
resistor should be
placed in series with the positive input for other AD9631
noninverting and all AD9631 inverting configurations. The cor-
rect connection is shown in Figures 57 and 58.
+V
S
–V
S
V
IN
100–130
0.1
μ
F
10
μ
F
6
7
2
4
3
0.1
μ
F
10
μ
F
R
F
R
G
R
IN
V
OUT
G = 1 + R
F
R
G
AD9631/32
R
TERM
Figure 57. Noninverting Operation
+V
S
–V
S
V
IN
100–130
0.1
μ
F
10
μ
F
6
7
2
4
3
0.1
μ
F
10
μ
F
R
F
R
G
R
TERM
V
OUT
G = – R
F
R
G
AD9631/32
R
IN
Figure 58. Inverting Operation
When the AD9631 is used in the transimpedance (I to V) mode,
such as in photodiode detection, the value of R
F
and diode ca-
pacitance (C
I
) are usually known. Generally, the value of R
F
se-
lected will be in the k
range, and a shunt capacitor (C
F
) across
R
F
will be required to maintain good amplifier stability. The
value of C
F
required to maintain optimal flatness (<1 dB Peak-
ing) and settling time can be estimated as:
[
where
ω
O
is equal to the unity gain bandwidth product of the
amplifier in rad/sec, and C
I
is the equivalent total input
capacitance at the inverting input. Typically
ω
O
= 800
×
10
6
rad/sec (see Open-Loop Frequency Response curve (Fig-
ure 17).
As an example, choosing R
F
= 10 k
and C
I
= 5 pF, requires
C
F
to be 1.1 pF (Note: C
I
includes both source and parasitic
circuit capacitance). The bandwidth of the amplifier can be es-
timated using the C
F
calculated as:
C
F
(2
ω
O
C
I
R
F
–1)/
ω
O
2
R
F
2
]
1/2
f
3
dB
1.6
2
π
R
F
C
F
R
F
V
OUT
AD9631
C
F
C
I
I
I
Figure 59. Transimpedance Configuration
相關(guān)PDF資料
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