參數資料
型號: LT6350HDD#TRPBF
廠商: Linear Technology
文件頁數: 11/28頁
文件大?。?/td> 0K
描述: IC DIFF CONVERT/ADC DRIVER 8-DFN
標準包裝: 2,500
類型: ADC 驅動器
應用: 數據采集
安裝類型: 表面貼裝
封裝/外殼: 8-WFDFN 裸露焊盤
供應商設備封裝: 8-DFN-EP(3x3)
包裝: 帶卷 (TR)
配用: DC1783A-H-ND - BOARD SAR ADC LTC2376-18
DC1783A-G-ND - BOARD SAR ADC LTC2377-18
DC1783A-F-ND - BOARD SAR ADC LTC2378-18
DC1783A-E-ND - BOARD SAR ADC LTC2379-18
DC1783A-D-ND - BOARD SAR ADC LTC2376-16
DC1783A-C-ND - BOARD SAR ADC LTC2377-16
DC1783A-B-ND - BOARD SAR ADC LTC2378-16
DC1783A-A-ND - BOARD SAR ADC LTC2380-16
DC1500A-C-ND - BOARD SAR ADC LTC2391-16
DC1500A-B-ND - BOARD SAR ADC LTC2392-16
LT6350
19
6350fc
For more information www.linear.com/LT6350
applicaTions inForMaTion
Becausetheinputbiascurrentintoopamp2ismuchlarger
than the offset current, choosing R+IN2tobeRINT/2greatly
reducestheoffsetcontributionofopamp2’sinputcurrents
on all units. With R+IN2 = RINT/2, VOSCM reduces to:
VOSCM = VOS2 – (IOS2/2) RINT
VOSCM is trimmed to within ±125V with a 499Ω resistor
installed at +IN2.
The value of VOS1 is trimmed to bring VOSDIFF to ± 125V.
Because linear modulation of VOS1 with input common
mode could degrade the common mode rejection ratio
specification of op amp 1, and nonlinear modulation of
VOS1 could cause nonlinear gain error (distortion), VOS1
is trimmed to a low constant value over as wide an input
common mode range as possible. A precision, 2-point
trim algorithm is used that results in VOS1 within ±125V
over the input range V+ 1.3V ≤ V+IN1 ≤ V+ and VOS1
within ±300V over the input range V≤ V+IN1 ≤ V+. A
negative supply below –1.3V can be used to extend the
input range for which VOS1 is within ±125V all the way
down to ground.
As a result of the trim procedure, the lowest offsets, both
common mode and differential mode, will occur with a
499Ω resistor at +IN2. This resistor can be bypassed with
a capacitor to eliminate its noise contribution. The gain-
setting resistor network (RG and RF) impedance should
be matched to that of the source to minimize op amp 1’s
input bias current contributions to the offsets.
NOISE CONSIDERATIONS
AmodelshowingthesourcesofoutputnoiseintheLT6350
is shown in Figure 8. The total output noise resulting from
all contributors is governed by the equation:
The LT6350 uses very low noise op amps, resulting in a
total differential output spot noise at 10kHz of 8.2nV/√Hz
when the LT6350 is in the noninverting gain-of-two con-
figuration shown in Figure 2. This is equivalent to the
voltage noise of a 1015Ω resistor at the +IN1 input. For
source resistors larger than about 1k, voltage noise due to
the source resistance will start to dominate output noise.
Source resistors larger than about 13k will interact with
the input current noise and result in output noise that is
resistor noise and amplifier current noise dominant.
+
RG
RS
R+IN2
RF
RINT
in1
en1
enRF
enRG
enRS
eno1
eno2
–IN1
+IN1
+IN2
OP AMP 1
OP AMP 2
6350 F08
enRINT
en2
enR+IN2
in2
+
eno
Figure 8. Noise Model
Note that the parallel combination of gain-setting resis-
tors RF and RG behaves like the source resistance, RS,
from the point of view of noise calculations, and the value
should be kept below about 1k to avoid increasing the
output noise. Lower-value gain and feedback resistors,
eno = √(4 [e2n1 + (in1RS)2 + e2nRS](1 + (RF/RG))2 + 4 (in1RF)2 + 4e2nRF (1 + (RF/RG)) + 4e2n2 + 4e2nR+IN2 +
2e2nRINT + (in2RINT)2 + 4 (in2R+IN2)2 )
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