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參數(shù)資料
| 型號： | AD797BR-REEL7 |
| 廠商： | Analog Devices Inc |
| 文件頁數(shù)： | 5/20頁 |
| 文件大小： | 0K |
| 描述： | IC OPAMP GP 110MHZ ULDIST 8SOIC |
| 標準包裝： | 750 |
| 放大器類型： | 通用 |
| 電路數(shù)： | 1 |
| 轉換速率： | 20 V/µs |
| 增益帶寬積： | 110MHz |
| -3db帶寬： | 8MHz |
| 電流 - 輸入偏壓： | 250nA |
| 電壓 - 輸入偏移： | 10µV |
| 電流 - 電源： | 8.2mA |
| 電流 - 輸出 / 通道： | 50mA |
| 電壓 - 電源，單路/雙路(±)： | ±5 V ~ 15 V |
| 工作溫度： | -40°C ~ 85°C |
| 安裝類型： | 表面貼裝 |
| 封裝/外殼： | 8-SOIC（0.154"，3.90mm 寬） |
| 供應商設備封裝： | 8-SO |
| 包裝： | 帶卷 (TR) |
Data Sheet
AD797
Rev. J | Page 13 of 20
BYPASSING CONSIDERATIONS
Taking full advantage of the very wide bandwidth and dynamic
range capabilities of the AD797 requires some precautions.
First, multiple bypassing is recommended in any precision
application. A 1.0 μF to 4.7 μF tantalum in parallel with 0.1 μF
ceramic bypass capacitors are sufficient in most applications.
When driving heavy loads, a larger demand is placed on the
supply bypassing. In this case, selective use of larger values of
tantalum capacitors and damping of their lead inductance with
small-value (1.1 Ω to 4.7 Ω) carbon resistors can achieve an
improvement. Figure 36 summarizes power supply bypassing
recommendations.
USE SHORT
LEAD LENGTHS
(<5mm)
KELVIN RETURN
LOAD
CURRENT
OR
0.1F
VS
4.7F
00846-
035
USE SHORT
LEAD LENGTHS
(<5mm)
KELVIN RETURN
LOAD
CURRENT
0.1F
4.7F TO 22.0F
1.1 TO 4.7
Figure 36. Recommended Power Supply Bypassing
THE NONINVERTING CONFIGURATION
Ultralow noise requires very low values of the internal parasitic
resistance (rBB) for the input transistors (≈6 Ω). This implies
very little damping of input and output reactive interactions.
With the AD797, additional input series damping is required
for stability with direct output to input feedback. A 100 Ω
resistor (R1) in the inverting input (Figure 37) is sufficient; the
100 Ω balancing resistor (R2) is recommended but is not
required for stability. The noise penalty is minimal (eNtotal ≈
2.1 nV/√Hz), which is usually insignificant.
7
4
3
R2
100
R1
100
*
VOUT
VIN
+VS
–VS
AD797
00846-
036
RL
600
6
2
*USE THE POWER SUPPLY BYPASSING SHOWN IN FIGURE 35.
Figure 37. Voltage Follower Connection
Best response flatness is obtained with the addition of a small
capacitor (CL < 33 pF) in parallel with the 100 Ω resistor
(Figure 38). The input source resistance and capacitance also
affect the response slightly, and experimentation may be
necessary for best results.
7
*
*USE THE POWER SUPPLY BYPASSING SHOWN IN FIGURE 35.
*
VOUT
VIN
+VS
–VS
AD797
00846-
037
CL
6
2
RS
CS
3
4
600
100
Figure 38. Alternative Voltage Follower Connection
Low noise preamplification is usually performed in the non-
inverting mode (Figure 39). For lowest noise, the equivalent
resistance of the feedback network should be as low as possible.
The 30 mA minimum drive current of the AD797 makes it easier
to achieve this. The feedback resistors can be made as low as
possible, with consideration to load drive and power consumption.
7
*
VOUT
VIN
+VS
–VS
AD797
00846-
038
RL
CL
R2
R1
6
2
3
4
*USE THE POWER SUPPLY BYPASSING SHOWN IN FIGURE 35.
Figure 39. Low Noise Preamplifier
used as a low noise follower. Operation on 5 V supplies allows
the use of a 100 Ω or less feedback network (R1 + R2). Because
the AD797 shows no unusual behavior when operating near its
maximum rated current, it is suitable for driving the AD600/
AD602 (see Figure 51) while preserving low noise performance.
Optimum flatness and stability at noise gains >1 sometimes require
a small capacitor (CL) connected across the feedback resistor (R1 of
gains. In general, when R2 is greater than 100 Ω and CL is greater
than 33 pF, a 100 Ω resistor should be placed in series with CL.
Source resistance matching is assumed, and the AD797 should not
be operated with unbalanced source resistance >200 kΩ/G.
Table 6. Values for Follower with Gain Circuit
Gain
R1
R2
CL
Noise
(Excluding RS)
2
1 kΩ
≈ 20 pF
3.0 nV/√Hz
2
300 Ω
≈ 10 pF
1.8 nV/√Hz
10
33.2 Ω
300 Ω
≈ 5 pF
1.2 nV/√Hz
20
16.5 Ω
316 Ω
1.0 nV/√Hz
>35
10 Ω
(G 1) × 10 Ω
0.98 nV/√Hz
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