參數(shù)資料
型號: IR3638SPBF
廠商: International Rectifier
英文描述: HIGH FREQUENCY SYNCHRONOUS PWM BUCK CONTROLLER FOR TRACKING APPLIACTIONS
中文描述: 高頻同步PWM降壓控制器進行跟蹤APPLIACTIONS
文件頁數(shù): 11/15頁
文件大?。?/td> 300K
代理商: IR3638SPBF
IR3638SP
b
F
3/19/07
Power MOSFET Selection (Cont..)
The IRF8910 has the following data:
The conduction losses will be:
P
con
=0.724W
The switching loss is more difficult to calculate,
even though the switching transition is well
understood. The reason is the effect of the
parasitic components and switching times during
the switching procedures such as turn-on / turn-
off delays and rise and fall times. The control
MOSFET contributes to the majority of the
switching losses in synchronous Buck converter.
The synchronous MOSFET turns on under zero
voltage conditions, therefore, the turn on losses
for synchronous MOSFET can be neglected.
With a linear approximation, the total switching
loss can be expressed as:
Where:
V ds(off) = Drain to source voltage at the off time
t
r
= Rise time
t
f
= Fall time
T = Switching period
Iload = Load current
The switching time waveforms is shown in
figure9.
V
DS
90%
V
10
V
m
4
.
13
R
A
@
10
Ω
I
,
V
20
=
)
V
gs
on
ds
d
ds
=
=
=
(
(7)
-
I
T
t
t
2
V
P
load
f
r
off
ds
sw
*
*
)
(
+
=
V
GS
10%
t
d
(ON)
t
d
(OFF)
t
r
t
f
Fig. 9: switching time waveforms
11
From IRF8910 data sheet:
t
r
= 10ns, t
f
= 4.1ns
These values are taken under a certain condition
test. For more details please refer to the IRF8910
data sheet.
By using equation (7), we can calculate the
switching losses.
P
sw
=0.37W
Feedback Compensation
The IR3638 is a voltage mode controller; the
control loop is a single voltage feedback path
including error amplifier and error comparator. To
achieve fast transient response and accurate
output regulation, a compensation circuit is
necessary. The goal of the compensation
network is to provide a closed loop transfer
function with the highest 0dB crossing frequency
and adequate phase margin (greater than 45
o
).
The output LC filter introduces a double pole, –
40dB/decade gain slope above its corner
resonant frequency, and a total phase lag of 180
o
(see figure 10). The resonant frequency of the LC
filter expressed as follows:
Figure 10 shows gain and phase of the LC filter.
Since we already have 180
o
phase shift just from
the output filter, the system risks being unstable.
The IR3638’s error amplifier is a differential-input
transconductance amplifier. The output is
available for DC gain control and AC phase
compensation.
The error amplifier can be compensated either in
type II or typeIII compensation. When it is used in
typeII
compensation
properties of the error amplifier become evident
and can be used to cancel one of the output filter
poles. This will be accomplished with a series RC
circuit from Comp pin to ground as shown in
figure 11.
This method requires that the output capacitor
should have enough ESR to satisfy stability
requirements. In general the output capacitor’s
ESR generates a zero typically at 5kHz to 50kHz
which is essential for an acceptable phase
margin.
the
transconductance
(8)
-
C
L
2
1
F
o
o
LC
=
π
Gain
F
LC
0dB
Phase
0
F
LC
-180
Frequency
Frequency
-40dB/decade
Fig. 10: Gain and Phase of LC filter
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