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參數(shù)資料
| 型號： | SA1638BE |
| 廠商： | NXP SEMICONDUCTORS |
| 元件分類： | 無繩電話/電話 |
| 英文描述： | Ceramic Multilayer Capacitor; Capacitance:47pF; Capacitance Tolerance:+/- 5 %; Working Voltage, DC:50V; Dielectric Characteristic:C0G/NP0; Package/Case:1206; Series:VJ; Features:Multilayer Ceramic Chip Capacitor |
| 中文描述： | TELECOM, CELLULAR, RF AND BASEBAND CIRCUIT, PQFP48 |
| 文件頁數(shù)： | 9/26頁 |
| 文件大?。?/td> | 271K |
| 代理商： | SA1638BE |
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Philips Semiconductors
Product specification
SA1638
Low voltage IF I/Q transceiver
1997 Sept 03
9
divide by 64. The division ratio is binary coded and set in the
registers n0 to n8. The default setting is a divide by 400.
At the completion of a main divider cycle, a main divider output is
generated which will drive the phase detector.
Phase Detector
The phase detector is a D-type flip-flop phase and frequency
detector shown in Figure 5. The flip-flops are set by the negative
edges of the output signals of the dividers. The rising edge of the
signal L will reset the flip-flops after both flip-flops have been set.
Around zero phase error this has the effect of delaying the reset for
1 reference input cycle. This avoids non-linearity or deadband
around zero phase error. The flip-flops drive on-chip charge pumps.
A source current from the charge pump acts to increase the VCO
frequency; a sink current acts to decrease the VCO frequency.
Current Setting
The charge pump current is defined by the current set between the
pin I
REF
and V
EE
CP. The current value to be set there is 31.2
μ
A.
This current can be set by an external resistor to be connected
between the pin I
REF
and V
EE
CP. The typical value R
EXT
(current
setting resistor) can be calculated with the formula
R
EXT
V
CC
CP
1.4V
31.2 A
The current can be set to zero by connecting the pin I
REF
to V
CC
CP.
Charge Pumps
The charge pumps at pin CP are driven by the phase dectector and
the current value is determined by the binary value of the charge
pumps register CN = c2, c1, c0, default 1mA. The active charge
pump current is typically:
|I
CP
|
(c0
2c1
4c2)
71 A
500 A
Lock Detect
The output LOCK is H when the phase detector indicates a lock
condition. This condition is defined as a phase difference of less
than
±
1 cycle on the reference input CLK
IN
, CLK
IN
X.
Test Modes (Synthesizer, Transmit Mixer)
The LOCK output is selectable as a test output. Bits x0, x1 control
the selection, the default setting is normal lock output as described
in the Lock detect section. The selection of a Bit x0, x1 combination
has a twofold effect: First it routes a divider output signal to the
LOCK pin, second it disables mixer stages in the transmit path.
Setting x0,1 = 11 disables both transmit path mixers. This mode can
be used to prevent the transmitter from producing an IF output
signal even if the transmit part is powered on (PDTx = 0V). This can
be used to simplify the control timing while commanding the transmit
and receive simultaneously without the transmit part causing
interference.
Table 1.
Test Modes
x0
x1
Synthesizer Sig
at LOCK Pin
Transmit Mixer
Q-mixer
on
I-mixer
on
0
0
normal lock detect
CLK
IN
divided by reference
divider ratio
LO
IN
÷
2 * (main divider ratio)
main divider output, that goes to
the phase detector
1
0
off
on
0
1
on
off
1
1
off
off
Status Register
The s0 and s1 status bits determine the values of the logic output
pins A
OUT
and B
OUT
. These outputs can be connected to the AGC
control inputs A and B of the SA1620. (See Figure 9)
DC Offset Register
Registers i0 to i3 and q0 to q3 control a correction to the output DC
offset of the I and Q channels of the receiver. The polarity of the DC
offset correction in the I and Q channels are determined by i0 and
q0, respectively. The other bits set the magnitude of the offset
correction. The step size of the two offset correction DACs is fixed
by an external resistor between the DCRES pin and ground. A
value of 120k
will give a step size of 200mV.
Mode Select Register
t0:
switches the RX IF gain.
t0 = 0
t0 = 1
no attenuation
10dB attenuation
The attenuation switch is included between the IF amplifier and the I
and Q mixers, thereby influencing the noise figure negligibly. The
purpose of this switch is to provide another AGC step which does
not influence the receiver noise figure. Please note that this gain
change will influence the DC offset of the I and Q mixers.
t1 = 0
test mode only, always to be set to 0.
t2, t3
sets the mode of the level locked loop (LLL)
The LLL is a circuit which processes the LO input signal in order to
provide an LO signal with a perfect 50% duty cycle, which
determines the precision of the 90
°
shift of the I and Q mixing
signals generated by the
÷
2 divider. For an external tuning of the
90
°
phase shift of the I and Q mixing signals, a trimming resistor
may be connected (but is not required) between the ADJ
IN
pin and
ground, and the LLL has to be put in one of the following modes:
Table 2.
t2
0
0
1
1
Mode Select Register
t3
0
1
0
1
LLL Status
LLL on (no external tune, monitor performance, default)
LLL on (with medium external tune)
LLL off (tune externally)
LLL on (with fine external tune)
t4
selects the bandwidth of the RC low pass filters at the I, Q
Rx mixer outputs
t4 = 0
cutt-off frequency (-3dB) 110kHz
t4 = 1
cutt-off frequency (-3dB) 792kHz
selects the bandwidth of the integrated 5th-order gyrator
filters. The filters are tuneable over a range of 50kHz to
1MHz with external resistors. The -3dB bandwidth is
inversely proportional to the value of the external resistor.
t5
With
t5, two external resistor values are selectable.
t5 = 0
the resistance between the pins RESA and
RESB determines the cutoff frequency. For
GSM a nominal bandwidth of 80kHz is chosen
when the external resistor is 36k
.
t5 = 1
a second resistor between the pins RESB and
RESD is connected in parallel to the first
external resistor, thus increasing the filter
bandwidth. The relative amplification is
decreased in this mode.
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