參數(shù)資料
型號(hào)： AD8310ARMZ-REEL7
廠商： Analog Devices Inc
文件頁(yè)數(shù)： 8/24頁(yè)
文件大?。?/td> 0K
描述： IC AMP LOGARITHMIC 8MSOP
標(biāo)準(zhǔn)包裝： 1,000
類(lèi)型： 對(duì)數(shù)放大器
應(yīng)用： 接收器信號(hào)強(qiáng)度指示（RSSI）
安裝類(lèi)型： 表面貼裝
封裝/外殼： 8-TSSOP，8-MSOP（0.118"，3.00mm 寬）
供應(yīng)商設(shè)備封裝： 8-MSOP
包裝： 帶卷 (TR)
AD8310
Rev. F | Page 16 of 24
FREQUENCY (MHz)
14
4
–1
60
150
80
DE
CIBE
LS
100
110
130
3
2
1
0
70
90
120
140
NARROW-BAND MATCHING
Transformer coupling is useful in broadband applications.
However, a magnetically coupled transformer might not be
convenient in some situations. Table 5 lists narrow-band
matching values.
GAIN
Table 5. Narrow-Band Matching Values
fC
(MHz)
ZIN
(Ω)
C1
(pF)
C2
(pF)
LM
(nH)
Voltage Gain
(dB)
10
45
160
150
3300
13.3
20
44
82
75
1600
13.4
50
46
30
27
680
13.4
100
50
15
13
270
13.4
150
57
10
8.2
220
13.2
200
57
7.5
6.8
150
12.8
250
50
6.2
5.6
100
12.3
500
54
3.9
3.3
39
10.9
10
103
100
91
5600
10.4
20
102
51
43
2700
10.4
50
99
22
18
1000
10.6
100
98
11
9.1
430
10.5
150
101
7.5
6.2
260
10.3
200
95
5.6
4.7
180
10.3
250
92
4.3
3.9
130
9.9
500
114
2.2
2.0
47
6.8
INPUT
9
8
7
6
5
13
12
11
10
01084-032
At high frequencies, it is often preferable to use a narrow-band
matching network, as shown in Figure 31. This has several advan-
tages. The same voltage gain is achieved, providing increased
sensitivity, but a measure of selectivity is also introduced. The
component count is low: two capacitors and an inexpensive chip
inductor. Additionally, by making these capacitors unequal, the
amplitudes at INP and INM can be equalized when driving from
a single-sided source; that is, the network also serves as a balun.
Figure 32 shows the response for a center frequency of 100 MHz;
note the very high attenuation at low frequencies. The high fre-
quency attenuation is due to the input capacitance of the log amp.
C1
C2
INLO
INHI
AD8310
SIGNAL
INPUT
LM
8
01084-031
1
Figure 31. Reactive Matching Network
Figure 32. Response of 100 MHz Matching Network
GENERAL MATCHING PROCEDURE
For other center frequencies and source impedances, the
following steps can be used to calculate the basic matching
parameters.
Step 1: Tune Out CIN
At a center frequency, fC, the shunt impedance of the input
capacitance, CIN, can be made to disappear by resonating with
a temporary inductor, LIN, whose value is given by
IN
C
L
2
1
ω
=
(5)
where CIN = 1.4 pF. For example, at fC = 100 MHz, LIN = 1.8 μH.
Step 2: Calculate CO and LO
Now, having a purely resistive input impedance, calculate the
nominal coupling elements, CO and LO, using
()
C
M
IN
O
M
IN
C
O
f
R
L
R
f
C
π
=
π
=
2
;
2
1
(6)
For the AD8310, RIN is 1 kΩ. Therefore, if a match to 50 Ω is
needed, at fC = 100 MHz, CO must be 7.12 pF and LO must be
356 nH.
Step 3: Split CO into Two Parts
To provide the desired fully balanced form of the network
shown in Figure 31, two capacitors C1 and C2, each of
nominally twice CO, can be used. This requires a value of
14.24 pF in this example. Under these conditions, the voltage
amplitudes at INHI and INLO are similar. A somewhat better
balance in the two drives can be achieved when C1 is made
slightly larger than C2, which also allows a wider range of
choices in selecting from standard values.
For example, capacitors of C1 = 15 pF and C2 = 13 pF can be
used, making CO = 6.96 pF.
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